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TPS54620RGYR

Part # TPS54620RGYR
Description Conv DC-DC Single Step Down 1.6V to 17V 14-Pin VQFN EP T/R
Category IC
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Technical Document


DISCLAIMER: The information provided herein is solely for informational purposes. Customers must be aware of the suitability of this product for their application, and consider that variable factors such as Manufacturer, Product Category, Date Codes, Pictures and Descriptions may differ from available inventory.

VOUT
R
ESR
C
O
R
L
VC
gm
ps
VOUT
R
ESR
C
O
R
L
VC
gm
ps
fp
fz
Adc
s
1+
2 z
VOUT
= Adc
VC
s
1+
2 p
æ ö
ç ÷
´ ¦
è ø
´
æ ö
ç ÷
´ ¦
è ø
p
p
(10)
ps L
Adc = gm R´
(11)
O L
1
p =
C R 2
¦
´ ´ p
(12)
O ESR
1
z =
C R 2
¦
´ ´ p
(13)
TPS54620
www.ti.com
........................................................................................................................................................................................................ SLVS949 MAY 2009
Figure 31. Simplified Small Signal Model for Peak Current Mode Control
Figure 32. Simplified Frequency Response for Peak Current Mode Control
Where
gm
ea
is the GM amplifier gain ( 1300 µ A/V)
gm
ps
is the power stage gain (16A/V).
R
L
is the load resistance
C
O
is the output capacitance.
R
ESR
is the equivalent series resistance of the output capacitor.
Copyright © 2009, Texas Instruments Incorporated Submit Documentation Feedback 19
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Small Signal Model for Frequency Compensation
Vref
VOUT
R1
R3
C1
C2
R2
CoeaRoea
gm
ea
COMP
VSENSE
Type 2A
Type 2B
R3
C1
ea ps
2 c VOUT Co
R3 =
gm Vref gm
´ ¦ ´ ´
´ ´
p
(14)
3. Place a compensation zero at the dominant pole
O L
1
p =
C R 2
æ ö
¦
ç ÷
´ ´
è ø
p
.
L
R Co
C1 =
R3
´
(15)
ESR
R Co
C2 =
R3
´
(16)
TPS54620
SLVS949 MAY 2009 ........................................................................................................................................................................................................
www.ti.com
The device uses a transconductance amplifier for the error amplifier and readily supports two of the commonly
used frequency compensation circuits shown in Figure 33 . In Type 2A, one additional high frequency pole is
added to attenuate high frequency noise.
The design guideline below are provided for advanced users who prefer to compensate using the general
method. The step-by-step design procedure described in the application section may also be used.
Figure 33. Types of Frequency Compensation
The general design guidelines for device loop compensation are as follows
1. Determine the crossover frequency fc
2. R3 can be determined by
Where
gm
ea
is the GM amplifier gain ( 1300 µ A/V)
gm
ps
is the power stage gain (16A/V).
Vref is the reference voltage (0.8V)
C1 can be determined by
4. C2 is optional. It can be used to cancel the zero from the ESR (Equivalent Series Resistance) of the output
capacitor Co.
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APPLICATION INFORMATION
Design Guide Step-By-Step Design Procedure
Typical Application Schematic
Operating Frequency
Output Inductor Selection
TPS54620
www.ti.com
........................................................................................................................................................................................................ SLVS949 MAY 2009
This example details the design of a high frequency switching regulator design using ceramic output capacitors.
A few parameters must be known in order to start the design process. These parameters are typically determined
at the system level. For this example, we start with the following known parameters:
Parameter Value
Output Voltage 3.3 V
Output Current 6 A
Transient Response 1A load step Δ Vout = 5 %
Input Voltage 12 V nominal, 8 V to 17 V
Output Voltage Ripple 33 mV p-p
Start Input Voltage (Rising Vin) 6.528 V
Stop Input Voltage (Falling Vin) 6.190 V
Switching Frequency 480 kHz
The application schematic of Figure 34 was developed to meet the requirements above. This circuit is available
as the TPS54620EVM-374 evaluation module. The design procedure is given in this section.
Figure 34. Typical Application Circuit
The first step is to decide on a switching frequency for the regulator. There is a trade off between higher and
lower switching frequencies. Higher switching frequencies may produce smaller a solution size using lower
valued inductors and smaller output capacitors compared to a power supply that switches at a lower frequency.
However, the higher switching frequency causes extra switching losses, which hurt the converter s efficiency and
thermal performance. In this design, a moderate switching frequency of 480 kHz is selected to achieve both a
small solution size and a high efficiency operation.
To calculate the value of the output inductor, use Equation 17 . KIND is a coefficient that represents the amount
of inductor ripple current relative to the maximum output current. The inductor ripple current is filtered by the
output capacitor. Therefore, choosing high inductor ripple currents impact the selection of the output capacitor
since the output capacitor must have a ripple current rating equal to or greater than the inductor ripple current. In
general, the inductor ripple value is at the discretion of the designer; however, KIND is normally from 0.1 to 0.3
for the majority of applications.
Copyright © 2009, Texas Instruments Incorporated Submit Documentation Feedback 21
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