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AD9880KSTZ-150

Part # AD9880KSTZ-150
Description PB-FREE 150 MHZ HDMI & ANALOGINTERFACE
Category IC
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Technical Document


DISCLAIMER: The information provided herein is solely for informational purposes. Customers must be aware of the suitability of this product for their application, and consider that variable factors such as Manufacturer, Product Category, Date Codes, Pictures and Descriptions may differ from available inventory.

AD9880
Rev. 0 | Page 13 of 64
This introduces a 700 mV dc offset to the signal, which must be
removed for proper capture by the AD9880.
The key to clamping is to identify a portion (time) of the signal
when the graphic system is known to be producing black. An
offset is then introduced which results in the ADCs producing a
black output (Code 0x00) when the known black input is
present. The offset then remains in place when other signal
levels are processed, and the entire signal is shifted to eliminate
offset errors.
In most pc graphics systems, black is transmitted between active
video lines. With CRT displays, when the electron beam has
completed writing a horizontal line on the screen (at the right
side), the beam is deflected quickly to the left side of the screen
(called horizontal retrace) and a black signal is provided to
prevent the beam from disturbing the image.
In systems with embedded sync, a blacker-than-black signal
(Hsync) is produced briefly to signal the CRT that it is time to
begin a retrace. For obvious reasons, it is important to avoid
clamping on the tip of Hsync. Fortunately, there is virtually
always a period following Hsync called the back porch where a
good black reference is provided. This is the time when
clamping should be done.
Clamp timing employs the AD9880 internal clamp timing
generator. The clamp placement register is programmed with
the number of pixel periods that should pass after the trailing
edge of Hsync before clamping starts. A second register (clamp
duration) sets the duration of the clamp. These are both 8-bit
values, providing considerable flexibility in clamp generation.
The clamp timing is referenced to the trailing edge of Hsync
because, though Hsync duration can vary widely, the back
porch (black reference) always follows Hsync. A good starting
point for establishing clamping is to set the clamp placement to
0x08 (providing 8 pixel periods for the graphics signal to
stabilize after sync) and set the clamp duration to 0x14 (giving
the clamp 20 pixel periods to reestablish the black reference).
For three-level syncs embedded on the green channel, it is
necessary to increase the clamp placement to beyond the posi-
tive portion of the sync. For example, a good clamp placement
(Register 0x19) for a 720p input is 0x26. This delays the start of
clamp by 38 pixel clock cycles after the rising edge of the three-
level sync, allowing plenty of time for the signal to return to a
black reference.
Clamping is accomplished by placing an appropriate charge on
the external input coupling capacitor. The value of this capa-
citor affects the performance of the clamp. If it is too small,
there is a significant amplitude change during a horizontal line
time (between clamping intervals). If the capacitor is too large,
then it takes excessively long for the clamp to recover from a
large change in incoming signal offset. The recommended value
(47 nF) results in recovering from a step error of 100 mV to
within ½ LSB in 10 lines with a clamp duration of 20 pixel
periods on a 75 Hz SXGA signal.
YUV Clamping
YUV graphic signals are slightly different from RGB signals in
that the dc reference level (black level in RGB signals) can be
at the midpoint of the graphics signal rather than the bottom.
For these signals it can be necessary to clamp to the midscale
range of the ADC range (128) rather than bottom of the ADC
range (0).
Clamping to midscale rather than ground can be accomplished
by setting the clamp select bits in the serial bus register. Each of
the three converters has its own selection bit so that they can be
clamped to either midscale or ground independently. These bits
are located in Register 0x1B [7:5]. The midscale reference
voltage is internally generated for each converter.
Auto Offset
The auto-offset circuit works by calculating the required offset
setting to yield a given output code during clamp. When this
block is enabled, the offset setting in the I
2
C is seen as a desired
clamp code rather than an actual offset. The circuit compares
the output code during clamp to the desired code and adjusts
the offset up or down to compensate.
The offset on the AD9880 can be adjusted automatically to a
specified target code. Using this option allows the user to set the
offset to any value and be assured that all channels with the
same value programmed into the target code will match. This
eliminates any need to adjust the offset at the factory. This
function is capable of running continuously anytime the clamp
is asserted.
There is an offset adjust register for each channel, namely the
offset registers at Addresses 0x08, 0x0A, and 0x0C. The offset
adjustment is a signed (twos complement) number with
±64 LSB range. The offset adjustment is added to whatever
offset the auto-offset comes up with. For example: using ground
clamp, the target code is set to 4. To get this code, the auto-
offset generates an offset of 68. If the offset adjustment is set to
10, the offset sent to the converter is 78. Likewise, if the offset
adjust is set to –10, the offset sent to the converter is 58. Refer to
application note AN-775, Implementing the Auto-Offset
Function of the AD9880, for a detailed description of how to
use this function.
Sync-on-Green (SOG)
The SOG input operates in two steps. First, it sets a baseline
clamp level off of the incoming video signal with a negative
peak detector. Second, it sets the sync trigger level to a
programmable level (typically 150 mV) above the negative
peak. The SOG input must be ac-coupled to the green analog
input through its own capacitor. The value of the capacitor must
be 1 nF ± 20%. If SOG is not used, this connection is not
AD9880
Rev. 0 | Page 14 of 64
required. Note that the SOG signal is always negative polarity.
For additional detail on setting the SOG threshold and other
SOG-related functions, see the
Sync Processing section.
05087-004
G
AIN
SOG
1nF
R
AIN
47nF
B
AIN
47nF
47nF
Figure 4. Typical Clamp Configuration for RGB/YUV Applications
Clock Generation
A PLL is employed to generate the pixel clock. In this PLL,
the Hsync input provides a reference frequency. A voltage
controlled oscillator (VCO) generates a much higher pixel clock
frequency. This pixel clock is divided by the PLL divide value
(Registers 0x01 and 0x02) and phase compared with the Hsync
input. Any error is used to shift the VCO frequency and
maintain lock between the two signals.
The stability of this clock is a very important element in provi-
ding the clearest and most stable image. During each pixel time,
there is a period during which the signal slews from the old
pixel amplitude and settles at its new value. This is followed by a
time when the input voltage is stable before the signal must slew
to a new value. The ratio of the slewing time to the stable time is
a function of the bandwidth of the graphics DAC and the
bandwidth of the transmission system (cable and termination).
It is also a function of the overall pixel rate. Clearly, if the
dynamic characteristics of the system remain fixed, then the
slewing and settling time is likewise fixed. This time must be
subtracted from the total pixel period, leaving the stable period.
At higher pixel frequencies, the total cycle time is shorter and
the stable pixel time also becomes shorter.
PIXEL CLOCK INVALID SAMPLE TIMES
05087-005
Figure 5. Pixel Sampling Times
Any jitter in the clock reduces the precision with which the
sampling time can be determined and must also be subtracted
from the stable pixel time. Considerable care has been taken in
the design of the AD9880’s clock generation circuit to minimize
jitter. The clock jitter of the AD9880 is less than 13% of the total
pixel time in all operating modes, making the reduction in the
valid sampling time due to jitter negligible.
The PLL characteristics are determined by the loop filter design,
the PLL charge pump current, and the VCO range setting. The
loop filter design is illustrated in
Figure 6. Recommended set-
tings of the VCO range and charge pump current for VESA
standard display modes are listed in
Table 8.
C
P
8nF
C
Z
80nF
R
Z
1.5kΩ
FILT
PV
D
05087-006
Figure 6. PLL Loop Filter Detail
Four programmable registers are provided to optimize the
performance of the PLL. These registers are
The 12-Bit Divisor Register. The input Hsync frequency
range can be any frequency which, combined with the
PLL_Div, does not exceed the VCO range . The PLL multi-
plies the frequency of the Hsync signal, producing pixel
clock frequencies in the range of 10 MHz to 100 MHz. The
divisor register controls the exact multiplication factor.
The 2-Bit VCO Range Register. To improve the noise
performance of the AD9880, the VCO operating frequency
range is divided into four overlapping regions. The VCO
range register sets this operating range. The frequency
ranges for the lowest and highest regions are shown in
Table 6.
Table 6.
VCORNGE Pixel Rate Range
00 12-30
01 30-60
10 60-120
11 120-150
The 5-Bit Phase Adjust Register. The phase of the
generated sampling clock can be shifted to locate an
optimum sampling point within a clock cycle. The phase
adjust register provides 32 phase-shift steps of 11.25° each.
The Hsync signal with an identical phase shift is available
through the HSOUT pin.
The COAST pin or the internal Coast is used to allow the PLL
to continue to run at the same frequency, in the absence of the
incoming Hsync signal or during disturbances in Hsync (such
as equalization pulses). This can be used during the vertical
sync period or any other time that the Hsync signal is unavail-
able. The polarity of the Coast signal can be set through the
Coast polarity register. Also, the polarity of the Hsync signal
can be set through the Hsync polarity register. For both Hsync
and Coast, a value of 1 is active high. The internal Coast
function is driven off the Vsync signal, which is typically a time
when Hsync signals can be disrupted with extra equalization
pulses.
AD9880
Rev. 0 | Page 15 of 64
Power Management
The AD9880 uses the activity detect circuits, the active interface
bits in the serial bus, the active interface override bits, the
power-down bit, and the power-down pin to determine the
correct power state. There are four power states: full-power,
seek mode, auto power-down and power-down.
Table 7 summarizes how the AD9880 determines which power
mode to be in and which circuitry is powered on/off in each of
these modes. The power-down command has priority and then
the automatic circuitry. The power-down pin (Pin 81—polarity
set by Register 0x26[3]) can drive the chip into four power-
down options. Bits 2 and 1 of Register 0x26 control these four
options. Bit 0 controls whether the chip is powered down or the
outputs are placed in high impedance mode (with the exception
of SOG). Bits 7 to 4 of Register 0x26 control whether the
outputs, SOG, Sony Philips digital interface (SPDIF ) or I2S (IIS
or Inter IC sound bus) outputs are in high impedance mode or
not. See the 2-Wire Serial Control Register Detail section for
the details.
Table 7. Power-Down Mode Descriptions
Inputs
Mode Power-Down
1
Sync Detect
2
Auto PD Enable
3
Power-On or Comments
Full Power 1 1 X Everything
Seek Mode 1 0 0 Everything
Seek Mode 1 0 1
Serial bus, sync activity detect, SOG, band gap
reference
Power-Down 0 X
Serial bus, sync activity detect, SOG, band gap
reference
1
Power-down is controlled via Bit 0 in Serial Bus Register 0x26.
2
Sync detect is determined by OR’ing Bits 7 to 2 in Serial Bus Register 0x15.
3
Auto power-down is controlled via Bit 7 in Serial Bus Register 0x27
Table 8. Recommended VCO Range and Charge Pump Current Settings for Standard Display Formats
Standard Resolution Refresh Rate Horizontal Frequency Pixel Rate VCO Range
1
Current
VGA 640 × 480 60 Hz 31.5 kHz 25.175 MHz 00 101
72 Hz 37.7 kHz 31.500 MHz 01 011
75 Hz 37.5 kHz 31.500 MHz 01 100
85 Hz 43.3 kHz 36.000 MHz 01 100
SVGA 800 × 600 56 Hz 35.1 kHz 36.000 MHz 01 100
60 Hz 37.9 kHz 40.000 MHz 01 101
72 Hz 48.1 kHz 50.000 MHz 01 110
75 Hz 46.9 kHz 49.500 MHz 01 110
85 Hz 53.7 kHz 56.250 MHz 01 110
XGA 1024 × 768 60 Hz 48.4 kHz 65.000 MHz 10 011
70 Hz 56.5 kHz 75.000 MHz 10 100
75 Hz 60.0 kHz 78.750 MHz 10 100
80 Hz 64.0 kHz 85.500 MHz 10 101
85 Hz 68.3 kHz 94.500 MHz 10 110
SXGA 1280 × 1024 60 Hz 64.0 kHz 108.000 MHz 10 110
1280 × 1024 75 Hz 80.0 kHz 135.000 MHz 11 110
TV 480i 60 Hz 15.75 kHz 13.51 MHz 00 010
480p 60 Hz 31.47 kHz 27 MHz 00 101
720p 60 Hz 45 kHz 74.25 MHz 10 100
1035i 60 Hz 33.75 kHz 74.25 MHz 10 100
1080i 60 Hz 33.75 kHz 74.25 MHz 10 100
1080p 60 Hz 67.5 KHz 148.5 MHz 11 110
1
These are preliminary recommendations for the analog PLL and are subject to change without notice.
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